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- Published: 08 February 2024
Design and optimization of metamaterial-based highly-isolated MIMO antenna with high gain and beam tilting ability for 5G millimeter wave applications
- Bashar A. F. Esmail 1 &
- Slawomir Koziel 1 , 2
Scientific Reports volume 14 , Article number: 3203 ( 2024 ) Cite this article
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- Electrical and electronic engineering
- Engineering
This paper presents a wideband multiple-input multiple-output (MIMO) antenna with high gain and isolation, as well as beam tilting capability, for 5G millimeter wave (MMW) applications. A single bow-tie antenna fed by a substrate-integrated waveguide (SIW) is proposed to cover the 28 GHz band (26.5–29.5 GHz) with a maximum gain of 6.35 dB. To enhance the gain, H-shaped metamaterial (MM)-based components are incorporated into the antenna substrate. The trust-region (TR) gradient-based search algorithm is employed to optimize the H-shape dimensions and to achieve a maximum gain of 11.2 dB at 29.2 GHz. The MM structure offers zero index refraction at the desired range. Subsequently, the MIMO system is constructed with two vertically arranged radiators. Another MM, a modified square resonator (MSR), is embedded between the two radiators to reduce the mutual coupling and to tilt the antenna main beam. Herein, the TR algorithm is again used to optimize the MSR dimensions, and to enhance the isolation to a maximum of 75 dB at 28.6 GHz. Further, the MSR can tilt the E-plane radiation by ± 20° with respect to the end-fire direction when alternating between the two ports' excitation. The developed system is validated experimentally with a good matching between the simulated and measured data.
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Introduction.
The emergence of fifth-generation (5G) technology is driven by the demand for broad bandwidth and high data rates to accommodate massive users. The millimeter-wave spectrum (MMW) offers an encouraging solution to enhance data rates and the capacity of 5G networks 1 . The International Telecommunications Union (ITU) has allocated various high-frequency bands to be associated with 5G, including 28, 38, and 60 GHz 2 . The 28 GHz (26.5–29.5 GHz) band is subject to extensive research for 5G networks, which exhibits significant performance enhancement over the 4G low frequencies. Nevertheless, the MMW band experiences high path losses, multipath fading effects, and interference as compared to sub-6 GHz bands 3 . High losses can be circumvented using high-gain antennas, whereas dual/multi-beam antennas are employed to conquer multipath fading and interference effects. The scientific literature reported a variety of techniques to enhance antenna gain, such as the use of multiple substrates 4 , the adoption of multiple shorting pins 5 , the incorporation of a dielectric lens 6 , and the utilization of artificial materials 7 , 8 . However, these approaches lead to bulky structures, complex power distribution, fabrication difficulties, narrow bandwidth, etc. It is evident that designing miniaturized high-gain antennas is a challenging task. Consequently, over the last two decades, metamaterials (MMs) have been utilized as a low-cost technique to enhance gain without significantly increasing the antenna profile. MMs constitute a remarkable class of synthetic materials that possess exceptional properties not found in nature. Various MM properties, including zero/near zero-index materials (ZIMs/NZIMs), low-index materials (LIMs), epsilon-near-zero (ENZ), mu-near-zero (MNZ), high refractive index (HRI), and negative refractive index (NRI), have been explored to design a broad range of antennas, especially in the context of gain enhancement 9 .
Improving the transmission quality in the MMW requires combining other available technologies, including MIMO, which has been identified as a key enabler of 5G. MIMO is a well-known diversity technique to enhance the resilience of communication when multiple antennas transmit/receive the same signal. This technique helps increase the channel capacity, spectrum efficiency, and data throughput, while reducing the impact of multipath effects 10 , 11 . Yet, a limited deployment volume of antenna systems may result in low isolation between MIMO elements, leading to system performance degradation. To address this, various techniques for reducing coupling have been suggested in the literature. These methods include introduction of decoupling networks and a neutralization line, as well as utilizing artificial materials 12 , 13 . Decoupling networks utilize explicit design procedures to systematically alleviate mutual coupling, whereas the neutralization line method is based on human intuition and lacks systematic procedures to improve isolation. Artificial materials with unique properties, such as electromagnetic band-gap (EBG) and metasurface, have been used as decoupling structures between radiating elements 14 , 15 . MMs can be embedded between MIMO radiators to mitigate the coupling without increasing the system's size and design complexity. Few reports utilized the MMs to improve the MIMO isolation at MMW 16 , 17 , 18 , 19 . The MM-based dielectric resonator antenna (DRA) was proposed to achieve high isolation of 29.3 dB and a gain of 7 dB at 28 GHz 16 . In 17 , a set of MMs was distributed between two microstrip antennas to improve the isolation by up to 40 dB and achieve a maximum gain of 8 dB at 30 GHz. Esmail et al. 18 improved the dual-band MIMO's isolation using MMs, achieving a maximum of 47 dB at 38 GHz. However, these findings showed a low gain of only 5 dB at 38 GHz. In 19 , isolation of two-port MIMO at 60 GHz was enhanced to 35 dB by inserting a vertically positioned MM array between the two DRAs.
On the other hand, directing an antenna's beam in a predefined direction plays a crucial role in enhancing the communication system's performance in terms of quality of service, security, interference avoidance, and power conservation 20 , 21 . This property can be realized conventionally by means of the phased array antenna and Butler matrix networks. Nevertheless, these methods exhibit limitations, which include high-cost, complex transceiver systems, and high-profile structures. Moreover, most of these techniques suffer from a decrease in gain 22 , 23 . To overcome these issues, MMs are employed to achieve beam tilting while maintaining a compact system size and simplicity. Further, they can enhance the antenna performance figures, such as gain and efficiency 24 , 25 . With the prompt progress in wireless communications, there is a swelling demand for broadband MIMO antennas with high isolation and gain, as well as beam tilting properties at the MMW band to meet the needs of the 5G networks.
In the light of the mentioned literature, none of the stated MIMO systems discussed the employment of the optimization techniques to attain high isolation and gain, as well as beam tilting property at the MMW spectrum. On the other hand, application of rigorous optimization techniques is instrumental in successful handling of multiple geometry parameters and design objectives, which cannot be achieved through traditional means such as experience-driven parametric studies. This paper addresses a design and optimization of a high-performance MIMO antenna for 28 GHz 5G applications. Two sets of MMs are employed to improve the system performance. The first set uses an H-shaped resonator to enhance the gain of the single antenna, followed by the implementation of MIMO and integration with a modified square resonator (MSR) between the radiators to achieve high isolation and a deflected beam in the E-plane. Performance parameters of the system are enhanced through formal two-stage optimization of the two MM structures. The contributions of this work are summarized as follows:
Design a broad-bandwidth MMW antenna based on substrate-integrated waveguide (SIW) and integrate the H-shape MM to enhance the gain.
Implementation of a two-port MIMO antenna and embedding the MSR array between the radiators to exhibit high isolation of up to 75 dB at 28.6 GHz, as well as achieving the E-plane radiation tilting when changing between MIMO ports.
Development and execution of a customized two-stage optimization approach to enhance the gain of the individual bow-tie antenna, and to reduce the MIMO mutual coupling and maintain the deflection angles of ± 20° at 28 GHz. The TR gradient-based search algorithm is employed to optimize the geometrical dimensional of the two MMs, and to enhance the antenna and MIMO performance while maintaining a low profile and simplicity. For that purpose, a regularization-based objective function is defined, which enables a simultaneous control over the single antenna gain and its reflection response, as well as the MIMO isolation, beam tilting, and the reflection response.
Compared to the state-of-the-art developments reported in the literature, the proposed design provides a low-cost, low-profile, and lower-complexity system with high gain and isolation, as well as the capability of tilting the E-plane radiation. The remaining part of the work is organized as follows. Section “ Antenna design ” introduces the antenna design. Section “ Gain enhancement based on optimized MMs ” elaborates on gain enhancement involving MMs. Optimization of the antenna‘s MMs is discussed in Section “ MMs antenna optimization ”. Sections “ MIMO design and isolation enhancement ” and “ MIMO performance optimization ” present the MIMO implementation with improved performance based on the optimized MSR structure. Experimental results and discussions are provided in Section “ Experimental results and discussion ”. The paper is concluded in Section “ Conclusion ”.
Antenna design
The configuration of the proposed antenna has been shown in Fig. 1 . It is essentially a bow-tie antenna fed by SIW. The structure consists of a microstrip line that feeds a microstrip-to-SIW transition, which, in turn, is connected to the front and the back parts of the bow-tie antenna. The antenna is printed on a Rogers RT5880 substrate with a thickness of 0.508 mm, dielectric constant of 2.2, and tangent loss of 0.0009. The SIW- based bow-tie antenna's dimensions are calculated using the set equations presented in 26 . The calculated values of s , a , b , and w c are 4.9 mm, 2.4 mm, 2.33 mm, and 0.3 mm, respectively, which are used to obtain the initial design of the SIW-inspired bow-tie. Numerical simulations are then employed to fine-tune and finalize the antenna design, where the simulated values are s = 5.2 mm, a = 2.56 mm, b = 2.5 mm, and w c = 0.2 mm. The presence of the SIW feed and inaccuracies in the design equations account for the minor discrepancy between the initial and final values. The SIW is employed to work as a wideband balun 27 . Both microstrip lines to the SIW and from the SIW to the two bow-tie arms are tapered to improve the impedance matching. Figure 2 depicts the antenna reflection coefficient and the gain. The results indicate that the antenna has a wide bandwidth of 3.8 GHz (26.2–30 GHz), making it suitable for covering the 5G band of 28 GHz. However, the maximum gain of 6.35 dB within the operational bandwidth is relatively low for MMW communications. There is a growing need for high-gain antennas to counteract the path loss experienced at the MMW spectrum. To address this, MMs have been integrated with antennas to boost their gain performance.
The configuration of the SIW-based antenna, ( a ) antenna geometry (The antenna dimensions are: a = 2.56, mm, b = 2.5 mm, L = 1.1 mm, L 1 = 1.5 mm, L 2 = 5 mm, L 3 = 4 mm, L 4 = 2.7 mm, L 5 = 6.7 mm, s = 5.2 mm, w c = 0.2 mm, w = 1.4 mm, w 1 = 2.7 mm, w 2 = 1.85 mm, p = 0.69 mm, d = 0.36 mm.), and ( b ) 3D view with the end-launch connector.
The antenna reflection coefficient and the realized gain.
Gain enhancement based on optimized MMs
An array of modified H-shaped MMs has been added to the antenna substrate in the end-fire direction (the xy -plane) to augment the gain. Figure 3 illustrates the antenna configuration with the MMs incorporated. By inserting the intial MMs into the antenna substrate and appropriate numerical optimization of their geometry parameters, it is possible to shorten the design cycle, including the adjustments to geometry dimensions, while achieving the optimum design. In this context, optimization of the MMs embedded into the antenna system (rather than designing the structure separately and then integrating it into the antenna substrate, which necessitates re-optimizing the number and location of unit cells), allows for saving time and resources, as compared to carrying out these stages separately. The reflection coefficient and gain plots of the stand-alone antenna and the MM antenna (before and after the optimization) have been depicted in Fig. 4 . It can be observed that the inclusion of the MM has a minor impact on the impedance matching performance, where the bandwidth is only slightly shifted downwards to 26–29.8 GHz, compared to the initial antenna's bandwidth of 26.2–30 GHz. Nevertheless, the antenna remains capable of covering the 5G band (26.5–29.5 GHz). On the other hand, the stand-alone antenna's gain, which ranges from 5.8 to 6.35 dB in the 26.5–30 GHz band, is deemed insufficient for MMW communications. Before optimization, the initial H-shape design is incorporated in front of the radiation element. This preliminary design lacks the ZIM property, as indicated by the slight gain increase. As the gain of the antenna is known to be proportional to its aperture, the marginal gain increase before optimization can be attributed to the expansion of the substrate size to accommodate the MMs. The MM antenna's gain is notably enhanced prior to optimization, particularly below 29 GHz, compared to the stand-alone antenna. This suggests that further enhancements are achievable through suitable design optimization using formal numerical techniques. The TR gradient-based search procedure is employed to optimize the structure dimensions and to achieve a maximum gain of 11.2 dB at 29.2 GHz, cf. Figure 4 . The details of the optimization process can be found in Section “ MMs antenna optimization ”.
The configuration of the proposed antenna with the H-shaped MM structure.
The reflection coefficients and gains of the antenna without and with the MSR structure (before and after the optimization).
MMs antenna optimization
The proposed antenna is first optimized as a stand-alone (single) structure with the objective being gain enhancement. The adjustable parameters selected for the optimization process are x = [ Lu Wu Lu 2 Wu 1 ] T , all explained in Fig. 5 a. The parameter space X is set up using the following ranges: 0.6 ≤ Lu ≤ 3 mm, 0.6 ≤ Wu ≤ 1.5 mm, 0.2 ≤ Lu 2 ≤ 1 mm, and 0.2 ≤ Wu 1 ≤ 1.6 mm. Furthermore, we have the following constraints, which are imposed to ensure the geometrical consistency of the antenna structure: Lu 2 ≥ 0.2 mm, Lu 1 = ( Lu − 2 Lu 2 ) ≥ 0.2 mm, and Wu 1 ≤ Wu − 0.4.
( a ) Geometrical configuration of the optimized H-shaped resonator. (The dimensions are: Lu = 1.603 mm, Wu = 1.415 mm, Lu 1 = ( Lu-2* Lu 2 ) = 0.699 mm, Lu 2 = 0.452 mm, Wu 1 = 0.755 mm), ( b ) the electromagnetic wave propagation based on the ZIM layer.
The primary objective is to increase the average in-band gain G ( x ) within the frequency range F = [26.5 29.5] GHz. The secondary objective is to ensure that | S 11 ( x , f )| ≤ –10 dB for all f ∈ F . Consequently, the objective function (to be minimized) is defined as
are the mean realized gain and maximum in-band reflection, respectively. The optimum design x * is found by solving
Note that minimization of the objective function U leads to the improvement of the average gain, as well as enforcing the matching condition. The penalty coefficient β 28 is set to 100 to ensure that | S 11 ( x , f )| ≤ –10 dB over the bandwidth F within a tolerance of a fraction of dB. Formally speaking, the reflection requirement is an inequality constraint; however, due to being expensive to evaluate (required EM analysis), its implicit handling is more convenient 29 . The problem (4) is solved using the trust-region (TR) gradient-based algorithm 30 with antenna response sensitivities estimated using finite differentiation 31 . The TR procedure yields a series x ( i ) , i = 0, 1, …, of approximations to x * as x ( i +1) = argmin{ x ; || x – x ( i ) || ≤ d ( i ) : U L ( x )}, where the local objective function U L is defined as in (1) but evaluated using a first-order Taylor expansion model of antenna characteristics rather than directly through EM analysis. The search region size d ( i ) is adaptively adjusted using conventional TR rules 30 . The TR sub-problem is solved using the SQP algorithm 32 implemented in Matlab Optimization Toolbox 33 . The termination condition is convergence in argument (|| x ( i +1) – x ( i ) || < ε ; here, ε = 10 –3 ). The initial design x (0) = [2 1.2 0.2 0.3] T has been found using parametric studies. The optimized design obtained through optimization is x * = [1.603 1.415 0.452 0.755] T (dimensions in mm). The initial and optimized antenna responses can be found in Fig. 4 . The optimized MM unit cell is shown in Fig. 5 a. To ensure the required response, the boundary arrangement is assigned on all sides of the unit cell. The electric (magnetic) conductor boundary is allocated along the x ( z )-direction. The y -axis is set to propagate a normal incident electromagnetic wave. Along the y-axis, the normally incident electromagnetic wave propagates. The incident waves excite the resonator structure, and electromagnetic interaction occurs within the unit cell, creating resonance in the transmitted and reflected waves. Choosing the y-axis for exciting the unit cell is justified by the fact that MIMO antennas serve as the origin of the electromagnetic wave, propagating through the unit cells along the y-direction—the established mode of propagation for the MM unit cell, as elucidated above. The structure response and the retrieved constitutive parameters are presented in Fig. 6 a and b, respectively. The structure exhibits a zero-index characteristic within the desired range of 26.5–30 GHz, cf. Figure 6 b. The zero-index metamaterial (ZIM) functions as a meta-lens, concentrating radiation in the emission direction. The 3D radiation patterns of the SIW-based antenna at 28 GHz without and with ZIM are depicted in Fig. 7 a and b, respectively. The discernible change in the radiation pattern is evident in Fig. 7 b, illustrating the meta-lens property of the MM. With ZIM loading, the antenna radiation displays heightened directivity in the end-fire direction along the y-axis, leading to a notable gain enhancement, as portrayed in Fig. 4 . This remarkable feature, ZIM, can be leveraged to increase gain when combined with antennas. Gain enhancement can be explained using Snell's law of refraction, which is expressed as \(sin\theta i\cdot {n}_{i }=sin\theta r\bullet {n}_{r },\mathrm{ where}\) n i ( θ i ) and n r ( θ r ) represent the refractive indices (angles) of the incident and refraction rays. Figure 5 b depicts the wave propagation in both MM and air. Herein, when the incident rays pass from a medium of zero refractive index ( n i = n MM = 0) to a high refractive index medium ( n r = n air = 1), the refracted rays will disseminate in a path normal to the interface. Therefore, the phase change of the electromagnetic wave approaches/equals zero, leading to gain improvement in the emission direction.
H-shaped resonator performance: ( a ) S -parameters and ( b ) the constitutive parameters.
The 3D radiation patterns of the SIW-based antenna at 28 GHz, ( a ) without and ( b ) with ZIM.
MIMO design and isolation enhancement
As previously stated, the MIMO technology has been proposed to improve channel capacity, spectrum efficiency, and data throughput while reducing the multipath effects. To ensure optimal performance in such systems, minimizing mutual coupling is essential. Figure 8 illustrates the MM-based MIMO configuration, with radiators arranged adjacently. The reflection and transmission coefficients of the MIMO without MSRs are depicted in Fig. 9 . The system provides isolation of better than 26 dB over the desired band. The performance is acceptable, but there is a room for isolation improvement, which would be beneficial, especially in dense MIMO scenarios. Figure 10 a illustrates the E-plane radiation patterns for both ports, showing directive radiations towards the y -direction without any inclination. MMs offer a promising solution for minimizing mutual coupling compared to traditional methods. To boost isolation and to enable beam tilting in the end-fire direction ( y -direction), an array of MSRs has been integrated between the two radiators, as depicted in Fig. 8 . In most cases, achieving optimal performance in MM design hinges upon proper parameter tuning, and there exists no definitive formula that can be employed to design all MM structures. Consequently, utilization of formal optimization techniques represents the most efficient and effective means of obtaining desired outcomes in a shorter time frame and less effort.
The configuration of the developed MM-based MIMO system with the MSRs. The configuration of the developed MM-based MIMO system with the MSRs.
The S-parameters of the MIMO system without and with the MSR structure (before and after the optimization).
The E-plane radiation patterns of the MIMO system, ( a ) without and with MSR (before optimization), and ( b ) with MSR (after optimization).
MIMO performance optimization
The MIMO version of the proposed antenna is optimized to ensure the required tilt of the E-plane radiation pattern (here, α 0 = 20°) at 28 GHz, as well as to improve antenna isolation | S 21 | within the frequency range F = [26.5 29.5] GHz. Additional conditions are to maintain sufficient impedance matching | S 11 ( x , f )| ≤ –10 dB, and gain g ( x , f ) ≥ 9 dB for all f ∈ F . The design variables selected for the optimization purpose are x = [ Sl Sw Sl 2 Sw 1 Sw 2 Sl 1 ] T , all explained in Fig. 11 a. The parameter space X is set using the following ranges: 1 ≤ Sl ≤ 4 mm, 1.4 ≤ Sw ≤ 2.3 mm, 0.2 ≤ Sl 2 ≤ 0.5 mm, 0.7 ≤ Sw 1 ≤ 1.3 mm, 0.2 ≤ Sw 2 ≤ 0.4 mm, and 2.7 ≤ Sl 1 ≤ 4.5 mm. Additionally, we have three geometry constraints: Sw 1 ≤ (( Sw − 2 Sl 2 ) − 0.4), Sl 1 ≥ Sl , and Sw 2 ≤ Sw 1 − 0.4. The primary objective is to reduce the antenna isolation, defined as I ( x ) = max{ f ∈ F : | S 21 ( x , f )|} (i.e., as the maximum in-band transmission). The remaining conditions are handled as constraints. The objective function to be minimized is therefore defined as
where S ( x ) is defined in ( 3 ), the minimum in-band gain is defined as
whereas α ( x ) is the angle of maximum directivity extracted from the EM-simulated antenna farfield. The first two constraints are of inequality type with their violations quantified as relative ones, whereas the last one is the equality condition. The penalty coefficients are set to β 1 = β 2 = β 3 = 100. It should be noted that although matching and gain conditions are formally included into the objective function, they are to be almost automatically satisfied as the reflection coefficient and gain are only weakly-dependent on the parameters selected for isolation improvement. The initial design, obtained through parametric studies, is x (0) = [3.5 2.25 0.32 0.6 0.4 3.4] T [mm]. The optimized design x * = [2.984 2.102 0.342 0.968 0.203 3.573] T has been found by minimizing the objective function (5) similarly as in (4), using the trust-region algorithm outlined before. The initial and optimized antenna responses can be found in Figs. 8 and 9 .
The MSR configuration and its performance, ( a ) the structure. (The dimensions are: Sl = 2.984 mm, Sl 1 = 3.573 mm, Sl 2 = 0.342 mm, Sw = 2.102 mm, Sw 1 = 0.968 mm, Sw 2 = 0.203 mm), ( b ) S -parameters, and ( c ) the constitutive parameters.
Figure 11 a illustrates the MSR unit cell configuration, where the boundaries are established similarly to that of the H-shaped resonator. The structure consists of a square ring and two cross bars. The response of the structure and its constitutive parameters are presented in Fig. 11 b and c, respectively. Notably, the structure exhibits negative values of ɛ , μ , and n at the resonance frequency of 28.6 GHz. The optimized MSR offers high isolation in the desired band with a maximum of 75 dB at 28.6 GHz, with an enhancement of about 47 dB over the bare MIMO system, cf. Figure 9 . Further, the structure demonstrates a substantial permittivity of 6.5 and a refractive index of 2 at 28 GHz. It is worth noting that the actual substrate's refractive index is merely 1.6 34 . Hence, the proposed MM exhibits a significantly higher refractive index than the substrate, creating two different media with different refractive indices in the proximity of the radiator. This configuration causes the antenna beam to tilt toward the medium of a higher refractive index (MSR configuration). Excitation of Port 1 results in a + 20° tilt in the E-plane, whereas exciting Port 2 produces a deflection angle of − 20°, cf. Figure 10 b. The electric field distributions at 28.6 GHz for the MIMO system without and with MMs are presented in Fig. 12 a and b, where Port 1 is excited, and Port 2 is terminated by a 50-Ω load. During the simulation of the first antenna (Port 1) without the MMs, a significant mutual coupling field is evident at the second antenna (Port 2), as illustrated in Fig. 12 a. Conversely, with the inclusion of MMs, the coupling field diminishes at the second antenna, as shown in Fig. 12 b, resulting in a reduction of mutual coupling. The upper MSR unit cells play a more substantial role in minimizing mutual coupling. It's worth noting that the gain enhancement is substantiated by contrasting the electric fields of the bare MIMO and MM-based MIMO. The improvement in gain is evident as the field is distributed through the ZIMs, as shown in Fig. 12 b.
Electric field (V/m) distributions of the MIMO system at 28.6 GHz ( a ) without MMs and ( b ) with MMs.
Experimental results and discussion
The optimized MM-based MIMO has been fabricated to corroborate the numerical simulation outcomes and showcase its relevance for 5G applications. Figure 13 a displays the front and back views of the MIMO antenna prototype. An Anritsu vector network analyzer MS4644B (0–40 GHz) was utilized to measure the reflection and transmission coefficients. The radiation patterns were validated in an anechoic chamber, as depicted in Fig. 13 b. Figure 14 illustrates the comparison between the simulated and measured | S 11 | and mutual coupling | S 21 |. The developed MIMO provides a wide impedance bandwidth ranging from 26.2 to 30 GHz, effectively covering the 5G band of 28 GHz (26.5–29.5 GHz). One can observe a satisfactory alignment between both datasets for | S 11 |. Nonetheless, a slight difference in resonant magnitude is observed between the measured and simulated data. Measured isolation, | S 21 |, indicates a good agreement with simulation, especially in frequencies below 28 GHz. The measured isolation results, particularly above 28 GHz, are notably inconsistent with the simulated data due to various factors, including fabrication tolerance, cable loss, assembly inaccuracies, and the use of bulky and closely spaced end-launch connectors. Figure 15 displays the MM-based MIMO's simulated and measured realized gain plots when Port 1 is excited, and Port 2 is terminated with a 50-Ω load. In the desired band of 26.5–29.5 GHz, the simulated realized gain varies from 10 to 11 dB. The measured gain matches the simulation result for the entire band, although a minor discrepancy is observed at 28 GHz. This discrepancy is likely due to the same reasons mentioned earlier, such as manufacturing and antenna assembly inaccuracies, as well as angular inaccuracy in the antenna placement in the chamber. The co- and cross-polarization radiation patterns of the MM-inspired MIMO system in the E- and H-planes at 28 GHz are displayed in Fig. 16 . The radiation results are introduced individually for Port 1 and Port 2, cf. Figure 16 a and b, respectively. The developed system offers directional radiation in both planes with a low level of cross-polarized fields. Based on the ports excitation, the measured results confirm that the E-plane radiation is tilted by ± 20° at 28 GHz. The measured radiations correspond well with numerical simulation results for the E and H-planes at 28 GHz. Notably, the inactive port is terminated using the 50-Ω matched load during the measurements. The MM-based MIMO is investigated in terms of the envelope correlation coefficient (ECC) and diversity gain (DG) to appraise the system performance. The ECC can be computed using the field-based formula and directly calculate DG from the resulting ECC 17 . Figure 17 shows the ECC and DG plots. The ECC is < 0.5∙10 –4 in the range of 26.5–29.5 GHz, which is considerably below the acceptable threshold of 0.5 for wireless systems. Additionally, the DG values are in proximity to the standard value of 10 dB.
Fabrication and measurement: ( a ) front and back views of the MIMO prototype and ( b ) the MIMO antenna in the anechoic chamber.
Simulated and measured reflection and transmission coefficients.
Simulated and measured gain.
Simulated and measured radiation patterns of the developed MIMO system in the E- and H-planes at 28 GHz, ( a ) Port 1 and ( b ) Port 2.
The diversity performance of MIMO system, ECC and DG.
Table 1 illustrates a performance comparison between the proposed MM-based MIMO and state-of-the-art structures reported in the recent literature. In contrast to the recent findings, the MIMO antenna developed in this work exhibits the highest isolation and gain. Further, it boasts a compact and low-profile design, a broad bandwidth, and exceptional diversity performance while also providing a beam tilting capability.
The MM-based MIMO on single-layer Rogers PCB with broad bandwidth, high isolation and gain, and beam tilting capability in E-plane is reported for 5G MMW applications. The proposed antenna is a bow-tie structure fed by a SIW, covering a 5G band of 28 GHz, with H-shaped resonators integrated into the substrate to augment the gain. The H-shape dimensions are optimized using the TR algorithm to achieve zero index refraction within the desired range, thereby a maximum gain of 11.2 dB at 29.2 GHz. The MIMO system is then constructed using two vertically arranged radiators, with a modified square resonator (MSR) MM embedded between the radiators to reduce mutual coupling and to achieve beam tilting. The TR algorithm is employed to optimize the MSR dimensions and achieve a maximum isolation of 75 dB at 28.6 GHz, as well as E-plane radiation tilting of ± 20° in the end-fire direction when switching between the two ports. The MIMO system is experimentally validated, with a good matching between the simulated and measured data. Overall, this design offers a low-cost, low-profile, and less complex system with high isolation and gain as well as beam tilting capability compared to state-of-the-art developments in reported the literature. We believe that this design has the potential to be expanded to various antennas incorporating a range of MMs, allowing for the attainment of high-deflection angles in both the E- and H-planes. Furthermore, the system could be scaled to support multiple ports, beyond the current configuration of two, to further enhance 5G channel capacity.
Data availability
All data has been included in study.
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This work was partially supported by the Icelandic Centre for Research (RANNIS) Grant 239858 and by National Science Centre of Poland Grant 2022/47/B/ST7/00072.
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Conceptualization, B.A.F.E. (Bashar A.F. Esmail); Data curation, B.A.F.E., and S.K. (Slawomir Koziel); Formal analysis. B.A.F.E.; Funding acquisition, S.K.; Visualization, B.A.F.E.; Writing—original draft, B.A.F.E.; Writing—review and editing, S.K.; Sofware and Resources, B.A.F.E., and S.K.; Supervision, S.K.
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Esmail, B.A.F., Koziel, S. Design and optimization of metamaterial-based highly-isolated MIMO antenna with high gain and beam tilting ability for 5G millimeter wave applications. Sci Rep 14 , 3203 (2024). https://doi.org/10.1038/s41598-024-53723-8
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Design and Analysis of Multiband Antenna for Wireless Communication
- Published: 28 April 2020
- Volume 114 , pages 1389–1402, ( 2020 )
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- Manish Sharma ORCID: orcid.org/0000-0002-1539-2938 1
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In this manuscript a compact multiband antenna with dimension 16 × 18 × 0.787 mm 3 is presented for multiple wireless applications including Digital Cellular System (1.71–1.88 GHz), Personal Communication System (1.85–1.99Gz), Bluetooth Wireless System (2.402–2.480 GHz), WiMAX (3.30–3.80 GHz), WLAN (5.150–5.825 GHz) and X-Band Downlink System (7.25–7.75 GHz). Radiating patch consist of a glass shape and a rectangular ground plane. Two resonating bands (DCS, PCS and Bluetooth Wireless System) is obtained by inserting stubs whereas remaining bands (WiMAX, WLAN and X-Band Downlink System) is obtained by etching slots on the radiating patch. There is a close agreement between simulated and measured results which is obtained by fabricating prototype.
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Acknowledgements
Author is thankful to Krishna Ranjan Jha, Advance Microwave Antenna Testing Laboratory ( http://delhi.gov.in/wps/wcm/connect/doit_gbpec/GBPEC/Home/List+of+Labs ), G. B. Pant Engineering College, Delhi for providing Antenna Measurement Facility.
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Sharma, M. Design and Analysis of Multiband Antenna for Wireless Communication. Wireless Pers Commun 114 , 1389–1402 (2020). https://doi.org/10.1007/s11277-020-07425-9
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SRR metamaterial-based broadband patch antenna for wireless communications
- Preet Kaur ORCID: orcid.org/0000-0002-1125-3201 1 ,
- Sonia Bansal 1 &
- Navdeep Kumar 2
Journal of Engineering and Applied Science volume 69 , Article number: 47 ( 2022 ) Cite this article
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This paper presents the design and analysis of a broad-band patch antenna using split ring metamaterial. The SRR metamaterial structures are embedded in a unique and novel way in the patch antenna, so that subwavelength modes get introduced in the patch cavity and a broad bandwidth antenna with good performance characteristics is obtained. A rectangular microstrip patch antenna is taken as a reference antenna, which resonates at a frequency of 5.2 GHz and has an impedance bandwidth of 70 MHz. To improve the bandwidth of the patch antenna, firstly the split ring resonator (SRR) is designed according to the reference patch antenna. The optimized SRR metamaterial is placed in between the patch and ground plane of the proposed antenna. The – 10 dB impedance bandwidth of the metamaterial-embedded proposed antenna is 1.63–4.88 GHz and has an average gain of 4.5 dB. The Prototype of the proposed antenna and reference antenna is fabricated and experimental results are obtained. Experimental and simulated results are in good agreement. The presented antenna can be used for LTE, GSM, WiMAX, Bluetooth, and other wireless applications.
Introduction
In modern days, with the advancement in the wireless and electronics industry need for compact, broadband, high-gain, directional and low-cost antennas has increased very much because the antennas are the vital components in wireless communication system [ 1 ]. Patch antennas are low profile, have a simple geometric structure with the ability of easy fabrication on PCB and can be easily integrated with other wireless devices. So, these antennas are suitable for current wireless technology [ 2 ]. But one of the limitations of these antennas is narrow bandwidth. The bandwidth of patch antenna can be improved by embedding different shapes such as U shape and W shape in its ground plane [ 3 ], using a parasitic patch [ 4 ] and increase of substrate thickness. These techniques improve the bandwidth, but it reduces the efficiency of the antenna. Many other approaches like the slotted patch antenna technique, defected ground structures, merging of resonant modes [ 5 ], slotted array technique [ 6 ], and suspended techniques [ 7 ] are proposed in the literature. But these approaches have disadvantages of less improvement in bandwidth, complex structure, cross-polarization and impedance matching.
During the last few years, metamaterials have been the intense area of research in antenna design to improve antenna performance [ 8 , 9 , 10 , 11 , 12 , 13 ]. Metamaterials are artificial materials that exhibit properties that do not exist in naturally occurring materials. To improve the bandwidth of patch antenna different types of metamaterial [ 14 , 15 , 16 , 17 , 18 ] has been used by antenna designers for improving the bandwidth. A MIMO antenna with four ports is proposed by Xia Cao et al. [ 19 ] using a slotted square ring metamaterial structure to improve the bandwidth. Metamaterial-based imaging structure for wireless frequency range is presented in [ 20 ]. But the limitation of techniques used in these research works is that it improves the bandwidth, but it reduces the other performance parameters of the antenna and has complex antenna structures.
The main aim of this paper is to design a novel broadband patch antenna using metamaterial without degrading the other performance parameters of the antenna. The proposed technique in this paper uses 11 layers of SRR type MNG type metamaterial which are embedded between patch and ground plane. These SRR metamaterial structures are embedded in a unique and novel way in the patch antenna to improve the bandwidth of the reference patch antenna and make it broadband. The proposed patch antenna has wide bandwidth with good performance characteristics.
Design of reference antenna
A low-cost FR4 epoxy substrate with dielectric constant εr = 4.4 and loss tangent δ = 0.0025 is chosen for designing of reference antenna. The antenna is modeled and optimized in HFSS software. The optimized geometric parameters of the reference antenna are presented in Fig. 1 and fabricated antenna is presented in Fig. 2 . From Fig. 3 , it can be seen that the reference antenna resonates at a frequency of 5.2 GHz with a − 11.68 dB reflection coefficient (S11) and has a 70-MHz narrow impedance bandwidth. Figure 4 shows the measured and simulated gain in dB. The antenna has a gain of 4.02 dB at resonating frequency. The main drawback of this antenna is that it has a very narrow bandwidth and less return loss, which is not suitable for current wireless applications. So, SRR metamaterial is used in this paper to improve the bandwidth and overall performance of the antenna.
Geometric structure of optimized reference microstrip patch antenna
Fabricated reference patch antenna
Measured and simulated reflection coefficients of reference patch antenna
Measured and simulated gain of reference patch antenna
Design and analysis of unit cell of split ring resonator
A split ring resonator (SRR) comprises two concentric rings of copper printed on substrate material. Geometric parameters of SRR are presented in Fig. 5 a. Excitation of SRR with external magnetic field causes the current to flow from one ring structure to other through the slot between them. So, there is flow of very strong displacement current in this structure. The slots in SRR behaves like distributed capacitance and it behaves like LC circuit. The equivalent circuit of unit cell of SRR is presented in Fig. 5 b. In equivalent circuit, metallic ring structures are modeled by inductance L and capacitance C = Co/4 (Co/2 = capacitance due to single ring and structure behaves like LC circuit having resonant frequency given below as:
a Geometric structure of unit cell of SRR, Rout = 3 mm, Rin = 2.8 mm, w = 1 mm, s = 1 mm, S L = 10 mm, S w = 10 mm, b Equivalent circuit of unit cell of SRR
SRRs effective permeability can be given as
Unit cell of split ring resonator is modeled and simulated in HFSS as shown in Fig. 6 . For simulation of SRR metamaterial unit cell boundary conditions are used. Repeated unit cell boundary conditions are applied along x and y direction ( xy plane) and wave ports are applied in z direction as shown in Fig. 6 . The S parameters of optimized SRR structure are calculated and then permeability and permittivity are extracted from S parameters using the Eqs. ( 3 – 6 ).
Simulation model of unit cell of SRR (Unit cell boundary conditions are applied along x and y direction and wave ports are applied in z direction)
Real value of permeability (μ r ) and permittivity (ϵ r ) is shown in Fig. 7 . From permeability and permittivity graph it can be analyzed that real part of permeability of SRR at 5.4 GHz is negative and real part of permittivity is positive and maximum at his frequency, so this is MNG type resonating metamaterial. Refractive index ( \(n=\sqrt{\mu \varepsilon\ }\Big)\) is product of permittivity and permeability and is negative in this range. Figure 8 a, b shows E-field and the H-field of SRR structure. It shows that when SRR is excited with external magnetic field, it causes the current to flow from one ring structure to other through the slot between them. Hence there is a flow of strong displacement current in SRR structure.
Real permittivity and permeability of split ring resonator
a E-field of SRR structure. b H-field of SRR structure
Design and fabrication of proposed SRR-embedded patch antenna
For designing a broad-band antenna, optimized unit cell of SRRs is placed in between the patch antenna and ground plane. For this, the reference antenna substrate thickness is divided in two parts of 0.8 mm. The exploded view of SRR-embedded antenna is presented in Fig. 9 . Each layer of metamaterial placed under patch consist of four-unit cell of SRR.
Exploded view of proposed metamaterial (single layer)-embedded patch antenna in HFSS
The optimized SRR-embedded antenna consists of 11 layers of metamaterial to achieve maximum bandwidth.
The optimized and designed SRR-embedded antenna is fabricated using PCB prototyping machine. Figure 10 presents the fabricated SRR layer and Fig. 11 presents the fabricated proposed SRR-embedded patch antenna with 11 layers of metamaterial.
Fabricated single layer of metamaterial with four SRRs metamaterial
Fabricated proposed antenna with metamaterial layers placed under it
Results and discussion
Simulation and measured results of proposed srr-embedded patch antenna.
The proposed SRR antenna presented in Fig. 11 is simulated and optimized in HFSS. Reflection coefficient of fabricated antenna is measured using vector network analyzer (VNA). The gain and radiation patterns of antenna are measured in anechoic chamber. As the SRR is placed under patch, subwavelength modes get introduced in the patch antenna. Effect of adding the different layers of SRR underneath the patch is studied extensively in this paper. Addition of three layers under patch cause the patch to resonate at 3.8 GHz with impedance bandwidth of 80 MHz as presented in Fig. 12 . The antenna has gain of 4.05 dB at this frequency as presented in Fig. 12 . As the more layers of SRR is embedded under the patch it causes more modes to get introduced in patch antenna and resonant frequency also shift towards the lower side. Addition of five layers increases the bandwidth of patch antenna from 80 MHz to 150 MHz and addition of nine layers introduces one mode at frequency of 1.8 GHz and other two modes at 3.5 GHz and 4.5 GHz as presented in Fig. 13 .
Reflection coefficient and gain of three layers of SRR metamaterial-embedded antenna
Reflection coefficient of five and nine layers of SRR metamaterial-embedded antenna
When 11 layers of SRR is added all the three modes introduced by nine layers of metamaterial get merged and broad-bandwidth of 3.25 GHz is obtained. Figure 14 shows the simulated and measured reflection coefficient graph of proposed antenna with 11 layers of metamaterial. From this graph, it can be seen that antenna resonates between 1.62 GHz and 4.87 GHz and it covers the wide bandwidth of 3.25 GHz. The return loss of this proposed patch antenna improves from − 11.68 dB to − 25.2 dB and has average gain of 4.5 dB in the resonating frequency range of 1.63 GHz to 4.88 GHz as shown in Fig. 15 . Addition of more layers of metamaterial underneath the patch does not show further improvement in results. Hence, the proposed antenna has 11 layers of SRR under the patch. This antenna has good average gain of 4.5 dB in the entire resonating frequency range. Figure 16 presents the simulated and measured E-plane and H-plane radiation pattern of this antenna at 3.5 GHz. Proposed and reference antenna has almost same radiation pattern in both planes.
Simulated and measured reflection coefficient of proposed antenna with 11 layers of metamaterial
Simulated and measured gain of proposed antenna with 11 layers of metamaterial
Simulated and measured E plane ( a ) and H plane ( b ) radiation pattern of proposed antenna
Table 1 provides the comparison of various performance parameters of the reference antenna and proposed antenna. The conventional reference patch antenna produces a limited impedance bandwidth of 70 MHz. The SRR metamaterial improves the bandwidth of patch antenna significantly from 70 MHz to 3.25 GHz. Thus, bandwidth is multiplied by 46.42, which is huge improvement in bandwidth. The return loss of antenna also improves after embedding metamaterial and proposed antenna also has good gain in resonating frequency range. Due to introduction of various subwavelength modes in metamaterial-embedded antenna resonant frequency of reference antenna get shifted to lower frequency range of 1.63 GHz to 4.88 GHz from 5.4 GHz. All these subwavelength modes get merge and give rise to broad-bandwidth. Table 2 shows the comparison of proposed work with the other similar works. As per comparison, this can be concluded the embedding of SRR layer using proposed method gives significant improvement in bandwidth and designing and fabrication of proposed antenna is also very simple.
Conclusions
Developments of electronic warfare system and wireless communication in modern fast developing technologies include the use of metamaterial in antenna system for improving the performance of overall system. A broadband metamaterial-embedded antenna is proposed in this paper to adjust with current wireless systems. The presented antenna covers the frequency band of 1.63 GHz to 4.88 GHz is designed, analyzed and measured in this research paper. Simulated results shows that the presented antenna has bandwidth of 3.25 GHz (1.63–4.88 GHz) and the experimental results are close to simulated one. The proposed antenna has significant bandwidth and has average gain of 4.5 dB. The other advantages of proposed antenna are that it is cheap, simple, can be easy fabricated with PCB machine and can be integrated with other wireless devices. The presented antenna can be used for LTE, GSM, WiMAX, Bluetooth, and other wireless applications.
Availability of data and materials
The datasets generated during and/or analyzed during the current study are available from the corresponding author on reasonable request.
Abbreviations
Epsilion NeGative
Global System for Mobile Communications
High-frequency structure simulator
Long-term evolution
Printed circuit board
Split ring resonator
Worldwide Interoperability for Microwave Access
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Acknowledgements
We would like to acknowledge the support and guidance from Professor Dr. Asok de and Dr. S.K. Aggarwal during this research work.
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Kaur, P., Bansal, S. & Kumar, N. SRR metamaterial-based broadband patch antenna for wireless communications. J. Eng. Appl. Sci. 69 , 47 (2022). https://doi.org/10.1186/s44147-022-00103-6
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DOI : https://doi.org/10.1186/s44147-022-00103-6
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The antenna design exhibits a very wide operating bandwidth of 7.16 GHz over the frequency range of 1.87 GHz to 9.03 GHz with VSWR 2, return loss (S11) of 55.19 dB and radiation efficiency of 91. ...
This paper provides a comprehensive study of different antenna designs considering various 5G antenna design aspects like compactness, efficiency, isolation, etc. This review paper elaborates the state-of-the-art research on the different types of antennas with their performance enhancement techniques for 5G technology in recent years.
This paper explores the design, simulation, and analysis of a dual-band Microstrip patch antenna designed to operate efficiently at frequency ranges of 3.32 GHz-3.62 GHz and 4.72 GHz-6.83 GHz ...
Within a few years of its launch, 4G has now become primeval. Further, the need for the fifth generation of communication network is intensively being realized. In this paper, we design and simulate a microstrip patch antenna compatible with 5G communications. The antenna works in Extremely High Frequency (EHF) range at 43.7GHz.
The focus is not on impedance matching and rectifier design but rather is restricted to antenna design. Musa et al. reviewed the design of reconfigurable antennas using metamaterials. However, their work did not explore essential topics such as artificial intelligence, rectifiers, and the crucial synergy between the antenna, impedance matching ...
This review paper provides an overview of the latest developments in artificial intelligence (AI)-based antenna design and optimization for wireless communications. Machine learning (ML) and deep learning (DL) algorithms are applied to antenna engineering to improve the efficiency of the design and optimization processes. The review discusses the use of electromagnetic (EM) simulators such as ...
software, this antenna's design and simulation were completed. Coaxial probe feeding is used to supply this antenna.8 The E-shaped antenna array has been proposed utilizing a FR4 substrate, which has a 1.6 mm thickness and a dielectric constant of 4.2. The overall dimensions of the E-shaped microstrip patch antenna are 26.95 × 20.6 × 1.6 mm ...
The antenna is a critical part of the RF front end of a communication system. In this study, we present some of the major applications of artificial intelligence (AI) to antenna design. We review the previous research and applications of several AI techniques such as evolutionary algorithms, machine learning, and knowledge representation ontologies. Applications may vary from antenna design to ...
This paper proposes a new antenna design that is able to increase the performance level of IoT applications by means of an original design. The antenna was designed, simulated, tested, and evaluated in a real operating scenario. ... In recent years, the research interest in wearable antennas inserted on flexible materials [15,16,17] has ...
The manuscript summarizes the various MIMO antenna design aspects for NR FR-1 (new radio frequency range) and NR FR-2, which will benefit researchers in the field of 5G and forthcoming cellular generations. ... Feature papers represent the most advanced research with significant potential for high impact in the field. A Feature Paper should be ...
This paper addresses a design and optimization of a high-performance MIMO antenna for 28 GHz 5G applications. Two sets of MMs are employed to improve the system performance.
Designing a bite-sized 5G antenna is an adventurous task for researchers. This paper demonstrates a 28 GHz 5G antenna design and analysis. The foundation of this research is a rectangular patch antenna with a single rectangular slot. Rogers RT5880 with a thickness of 0.33 mm dielectric constant of 2.2 is used as substrate.
In this manuscript a compact multiband antenna with dimension 16 × 18 × 0.787 mm3 is presented for multiple wireless applications including Digital Cellular System (1.71-1.88 GHz), Personal Communication System (1.85-1.99Gz), Bluetooth Wireless System (2.402-2.480 GHz), WiMAX (3.30-3.80 GHz), WLAN (5.150-5.825 GHz) and X-Band Downlink System (7.25-7.75 GHz). Radiating patch ...
In this paper, a survey is presented on various antenna designs with their fabrication on different types of substrates such as Rogers RT/duroid 5880, Rogers RO4003C, Taconic TLY-5, etc., at ...
Finally, Section 4 concludes the paper. 2 RECONFIGURABLE METASURFACE ANTENNA DESIGN. Figure 1 depicts the layers of the proposed pattern-reconfigurable antenna. On the top of the first layer, the ground plane includes two coupling slots etched onto an RO4003C substrate with ε r = 3.38, tanδ = 0.0027, and a thickness of 0.203 mm.
This paper discusses various challenges related to the antenna design process for 5G communications focusing on the 26 GHz band. In a first example, an 8 element wideband array antenna is optimized for use in a mobile phone. The antenna performance is investigated, including gain, coupling and beamsteering. Aspects related to the antenna integration workflows are also discussed. In a second ...
design improvements instead of establishing an ideal printing condition for antenna implementation. This research aims to establish a unique, and cost-effective inkjet printing properties on the photo paper using silver nano ink. This step is followed by the fabrication of an
onal tools. The second part presents the research contribution published in the scienti c papers listed below. List of Included Papers I.D. Tayli and M. Gustafsson, \Physical Bounds for Antennas Above a Ground Plane" IEEE Antennas Wireless Propagation Letters, Vol. 15, pp. 1281{1284, 2015 Contributions of the author: The author of this thesis ...
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This paper presents the design and analysis of a broad-band patch antenna using split ring metamaterial. The SRR metamaterial structures are embedded in a unique and novel way in the patch antenna, so that subwavelength modes get introduced in the patch cavity and a broad bandwidth antenna with good performance characteristics is obtained. A rectangular microstrip patch antenna is taken as a ...
This paper discusses the state-of-the-art wearable/textile/flexible antennas integrated with metamaterial structures composed of wearable/flexible substrate materials, with a focus on single and dual band antenna designs. The paper also reviews the critical design issues, various fabrication techniques, and other factors that need to be ...
This paper presents a multiple-input and multiple-output (MIMO) antenna design for the 5G/B5G Internet of Things (IoT). The proposed MIMO antenna is designed to operate at multiple bands, i.e., at 3.5 GHz, 3.6 GHz, and 3.7 GHz microwave Sub-6 GHz and 28 GHz mm-wave bands, by employing a single radiating aperture, which is based on a tapered ...
The paper describes compact fractal antennae combined with ground defected structures (DGS) and substrate integrated waveguide (SIW) techniques for enhancing resonate and multiband behavior concerning bandwidth, gain, and radiation in the desired mm-wave region.